Audio amplifier and methods of generating audio signals

ABSTRACT

Audio amplifiers and methods of generating audio signals are disclosed. A disclosed example amplifier comprises a first driver to receive a first signal; a second driver to receive a second signal; a configurable signal delivery circuit; and a mode selector in communication with the first and second drivers to selectively configure the signal delivery circuit in a voltage boost mode or a voltage buck-boost mode based on a characteristic of the input signal.

FIELD OF THE DISCLOSURE

The present disclosure relates generally to audio signal processing and, more particularly, to audio amplifiers and methods of generating audio signals.

BACKGROUND

In portable electronic devices having acoustic elements (e.g., cellular phones, two-way radios, etc.), advances in piezo-electric speakers have increased the audio fidelity experienced by end users. However, piezo-electric speakers generally require large voltages (e.g., greater than 10 V_(RMS)) to provide high fidelity audio. These high voltages present challenges in the context of portable devices, which generally use low voltage power sources to preserve battery power. Such devices have addressed this issue by employing a voltage booster, which, in turn, powers an amplifier to amplify the audio signal to power the piezo-electric speaker(s). Known audio amplifiers employ a coupling capacitor to drive a single ended load. Alternatively, the power amplifier may be provided with a regulator or a charge pump to provide a second negative voltage supply.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a block diagram of an example ground-referenced audio amplifier driving a speaker.

FIG. 1A illustrates the example signal booster of FIG. 1 in greater detail.

FIG. 2 is a flow diagram of an example method that may be used to implement the example ground-referenced audio amplifier of FIG. 1.

FIG. 3 illustrates an example simulated signal output by the example circuit of FIG. 1 in response to an example input signal.

FIG. 4 is a schematic diagram of an example circuit implementing the ground-referenced audio amplifier 100 of FIG. 1.

FIGS. 5A and 5B illustrate example equivalent circuits of the example voltage booster and voltage buck-booster of FIG. 4.

FIG. 6 illustrates an example communication device 600 that may be used to implement the example ground-referenced audio amplifier 100 of FIG. 1.

FIGS. 7A-7D together comprise a schematic diagram of an example implementation of the circuits of FIGS. 1 and/or 4.

DETAILED DESCRIPTION

Example ground-referenced audio amplifiers and methods of generating an audio signal are disclosed herein. Although the example methods and apparatus described herein generally relate to ground-referenced audio amplifiers for mobile applications, the disclosure is not limited to mobile applications. On the contrary, the teachings of this disclosure may be applied in any device which would benefit from circuitry that achieves an amplified output voltage above a supply voltage and/or that would benefit from an amplification circuit and/or method that can provide a ground referenced output signal to a single-ended load from a single supply.

In the example of FIG. 1, an example ground-referenced audio amplifier 100 includes an input interface 102 to receive and filter an audio signal 103. The input interface 102 may utilize any suitable technique to prepare the signal 103 for further processing. For example, the input interface 102 may preprocess the signal 103 to reduce sensitivity to parameter variations, to level shift (e.g., DC bias) the input signal 103 to a desired level, to improve performance (e.g., noise, bandwidth, etc.), to increase high frequency performance, to improve stability, gain, etc. In the illustrated example audio amplifier, a second order control loop is utilized to improve performance of the audio amplifier by filtering switching noise, increasing gain, and increasing stability. Second order control loops of this type have been employed in class D amplifiers.

The input interface 102 of the illustrated example conveys the preprocessed audio signal to a pulse width modulator (PWM) 104. The PWM 104 may modulate the preprocessed audio signal received from the input interface 102 based on any technique (e.g., intersective, delta, sigma-delta, etc.). In the example of FIG. 1, a triangle signal is provided as a reference signal to modulate the preprocessed audio signal to form a first PWM signal and a second PWM signal. The first PWM signal is based on a comparison of the preprocessed audio signal and the reference signal. The second PWM signal is based on an inverse comparison of the preprocessed audio signal and the reference signal. The first PWM signal is indicative of a characteristic (e.g., a voltage, a current, the power spectral density, etc) of the audio signal 103. The second PWM signal is also indicative of the characteristic (e.g., the amplitude and/or the power spectral density) of the audio signal 103. However, the characteristic represented by the second PWM signal is the inverse of the characteristic represented by the first PWM signal.

The first and the second PWM signals are conveyed to a mode selector 106. The mode selector 106 also receives the preprocessed audio signal via the input interface 102. Based on a characteristic of the preprocessed audio signal, the mode selector 106 determines whether the first PWM signal will be conveyed to a low-side output driver 110 or whether the second PWM signal will be conveyed to a high-side output driver 108. In other words, the mode selector 106 selects the output path of the example audio amplifier 100 based on a characteristic of the preprocessed audio signal. For example, if the mode selector 106 determines that the characteristic of the audio signal has a first state (e.g., the voltage of the preprocessed audio signal exceeds a threshold), the mode selector 106 conveys the first PWM signal to the high-side output driver 108. If the mode selector 106 determines that the characteristic of the preprocessed audio signal has a second state (e.g., the voltage of the preprocessed audio signal does not exceed the threshold), the mode selector 106 conveys the second PWM signal to the low-side output driver 110.

The selected one of the high-side output driver 108 and the low-side output driver 110 of the illustrated example configure a signal booster 112 to generate an output signal to be audibly presented to a user. In other words, when the low-side output driver 108 is selected, it causes the signal booster 112 to convert the first PWM signal into an output signal. When the high-side output driver is selected, it causes the signal booster 112 to generate an output signal based on the second PWM signal. When the high-side output driver 108 is selected, the low-side signal is not selected, and vice-versa (See FIG. 1A).

In the illustrated examples (See FIG. 1A), the signal booster 112 comprises an energy storage device 111 (e.g., an inductor) and configurable signal delivery circuitry 113. When the high-side output driver 108 is selected, the driver 108 configures the signal delivery circuitry 113 into a first configuration to cause the energy storage device 111 to deliver a first voltage of a first polarity (e.g., negative) to a load 114. The first voltage is an amplified version of a corresponding portion of the audio input signal 103. When the low-side output driver 110 is selected, the driver 110 configures the signal delivery circuitry 113 to cause the energy storage device 111 to deliver a second voltage of a second polarity (e.g., positive) to the load 114. The second voltage is an amplified version of a corresponding portion of the audio input signal 103. When the signal delivery circuitry 113 is in the first configuration, the example amplifier 100 is configured in a voltage buck-boost mode. When the signal delivery circuitry 113 is in the second configuration, the example amplifier 100 is in a voltage boost mode.

Irrespective of which mode is selected, an output signal comprising an amplified version of the audio input signal 103 is delivered to the load 114. For the typical input audio signal 103, the amplifier will repeatedly transition between the buck-boost mode and the boost mode in order to produce the amplified output signal.

In the illustrated example, the load 114 is a transducer (e.g., a speaker such as a piezo-electric speaker, a distributed mode actuator, etc.) that converts the output signal into a humanly audible output. In the illustrated example, the load 114 is coupled to a singled ended device and the amplifier 100 of the illustrated example is able to drive the load using a single voltage supply with a voltage of the output signal exceeding that voltage supply. This is particularly useful in low power applications such as portable electronics (e.g., cell phones, laptops, etc.) using piezo-electric speakers.

FIG. 2 is a flow chart of an example process 200 to audibly present an audio signal to a user of an example electronic device. In the example of FIG. 2, the example process 200 begins by receiving and preparing (e.g., level shifting, filtering, etc.) an audio signal 103 to be presented to a user (block 202). After preprocessing the audio signal, the audio signal is modulated to produce a first PWM signal and a second PWM signal (block 204). The first and second PWM signals are representative of at least some aspect of interest of the audio signal. After the first PWM signal and the second PWM signal are formed, the example process 200 determines if the portion of the preprocessed audio signal currently being prepared for reproduction at the load 114 exceeds a threshold (block 206). If the noted portion of the preprocessed audio signal exceeds the threshold, the example process 200 forms a boosted output signal based on the first PWM signal (block 208). On the other hand, if the noted portion of the preprocessed audio signal does not exceed the threshold, the example process 200 forms a buck-boosted output signal based on the PWM modulated signal (block 210). After forming the boosted output signal or buck-boosted output signal, the output signal is audibly presented to a user (block 212). Control continues to loop through blocks 206-214 until there is no more audio signal to process.

FIG. 3 illustrates an example output signal formed by the example audio amplifier 100 of FIG. 1 and/or FIG. 2 in response to an example input signal. In the example of FIG. 3, the input is an audio signal 103, and the output audio signal of the example method is an audio signal substantially corresponding to the audio signal, but with a larger voltage swing. In some examples, the audio amplifier 100 may distort the audio a small margin due to the devices of the audio amplifier 100 (e.g., noise of devices, non-linearities of devices, etc.). In the example of FIG. 3, the voltage of the power supply is shown by a dotted line labeled DC. As shown in FIG. 3, the example amplifier 100 is able to produce a voltage above the voltage of the power supply and a voltage below the voltage of the low output signal (e.g., a ground).

In some examples, the ground-reference audio amplifier 100 may be implemented by a voltage booster. FIG. 4 illustrates an example schematic diagram of a manner of implementing the ground-reference audio amplifier 100 of FIG. 1. In the example circuit 400 of FIG. 4, the input interface 102 is formed by an input resistance R_(I) 401, a direct current (DC) bias 402, a first integrator 404, a second integrator 406, and an amplifier 408. The audio signal is received by the input resistance 401 and then level shifted by the DC current bias 402. In the example of FIG. 4, the audio signal is level shifted such that any DC component of the audio signal is located at zero or substantially zero volts. The first integrator 404 receives the level shifted audio signal via a first input. The first integrator 404 also receives a second input corresponding to a DC voltage bias 412 via a second input. The DC voltage bias 412 may be implemented by any value (e.g., ½ V_(DD), 5 volts, 3.3 volts, 0 volts, etc.). A feedback loop 403 (including a resistor and a capacitor) couples the first input of the first integrator 404 with the output of the first integrator 404.

The output of the first integrator 404 is further coupled with a first input of the second integrator 406. The second integrator 406 also receives a second input corresponding to the DC bias 412 and has a feedback loop 405 (including a resistor and a capacitor) that couples the output of second integrator 406 with the first input of second integrator 406.

The amplifier 408 receives a first input from the second integrator 406 via an input resistance 409 and a second input from the second integrator 404 via a second input resistance 407. The amplifier 408 amplifies the difference in the output signal from the first integrator 404 and the output signal from the second integrator 406 to develop the preprocessed audio signal that is provided to the PWM 104. The preprocessed audio signal is also further amplified based on the voltage received from the DC bias 412. In the example of FIG. 4, the amplifier 408 also filters the audio signal to reduce noise (e.g., switching noise, noise from the feedback, noise from devices, etc.). From the foregoing, it will be recognized that the input interface 102 implements a second order feedback network to improve performance (e.g., gain, stability, etc.) of the example circuit 400

After the audio signal is pre-processed, the input interface 102 conveys the preprocessed audio signal to the PWM 104 and the mode selector 106. In the example of FIG. 4, the PWM 104 is implemented by a first comparator 414 and a second comparator 416. The first comparator 414 receives the preprocessed audio signal of the input interface 102 via a first (e.g., negative) input and also receives a reference signal (e.g., a triangle wave) via a second (e.g., positive) input. The comparator 414 compares the voltage of the preprocessed audio signal to the voltage of the reference signal. If the voltage of the preprocessed audio signal exceeds the voltage of the reference signal, the comparator 414 outputs a high voltage (e.g., 3.3 volts). On the other hand, if the voltage of the preprocessed audio signal does not exceed the voltage of the reference signal, the comparator outputs a low voltage (e.g., 0 volts). As a result, the comparator 414 forms a first PWM signal (e.g., a pulse train having a series of high voltages and low voltages) indicative of a characteristic of the audio signal such as the power spectral density of the audio signal.

The second comparator 416 of the PWM 104 receives the reference signal via its first (e.g., negative) input and also receives the preprocessed audio signal of the input interface 102 via its second (e.g., positive) input. The second comparator 416 compares the voltage of the reference signal to the voltage of the preprocessed audio signal. If the voltage of the reference signal exceeds the voltage of the preprocessed audio signal, the second comparator outputs a high voltage (e.g., 3.3 volts). On the other hand, if the voltage of the reference signal does not exceed the voltage of the preprocessed audio signal, the comparator outputs a low voltage (e.g., 0 volts). As a result, the second comparator 416 forms a second PWM signal indicative of a characteristic of the audio signal (e.g., the power spectral density of the preprocessed audio signal). The voltage of the second PWM signal has an opposite polarity relative to the first PWM signal.

The first PWM signal and the second PWM signal are conveyed from the PWM 104 to the mode selector 106. In the example of FIG. 4, the mode selector 106 also receives the DC voltage bias 412 and the preprocessed audio signal from the input interface 102. Based on a comparison of the preprocessed audio signal and the DC bias voltage 412, the mode selector 106 selects the operating mode (or output path) of the example circuit 400. In the illustrated examples, the mode selector is implemented by a comparator 420, a first switching device 422, an inverter 424, and a second switching device 426. The comparator 420 receives the preprocessed audio signal via a first (e.g., negative) input and the DC bias 412 via a second (e.g., positive) input. The comparator 420 compares the DC voltage bias and the preprocessed audio signal to determine if the voltage of the audio signal exceeds the voltage of the DC voltage bias 412.

If the voltage of the preprocessed audio signal exceeds the voltage of the DC bias 412, the comparator 420 outputs a high voltage (e.g., 3.3 volts). On the other hand, if the voltage of the audio signal does not exceed the voltage of the DC bias 412, the comparator 420 outputs a low voltage (e.g., 0 volts). The output of the comparator 420 is then conveyed to the first switching device 422 and to the second switching device 426 via the inverter 424.

The first switching device 422 receives the second PWM signal via a first input and also receives the output from the comparator 420 via a second input. In the example of FIG. 4, the switching device 422 is a logic OR gate. However, any type of active device may be used (e.g., a transistor, a circuit comprising multiple transistors, etc.) to implement the switching device 422. Because the switching device 422 of the illustrated example is an OR gate, when the output of the comparator 420 is high, the output of the OR gate 422 will be high irrespective of the state of the second PWM signal. Thus, when the output of the comparator 420 is high, the OR gate blocks the second PWM signal.

On the other hand, when the output of the comparator 420 is low, the output of the OR gate 422 will completely depend on the second PWM signal. When the output of the comparator 420 is low, the OR gate 422 passes the second PWM signal.

Put another way, the OR gate 422 has a first state in which it conveys a constant high voltage (i.e., when the voltage of the preprocessed audio signal exceeds the DC bias 412) applied to the comparator 420. However, when the voltage of the preprocessed audio signal does not exceed the DC bias 412) applied to the comparator 420, the switching device 426 enters a second state in which it outputs the second PWM signal.

As described above, the second switching device 426 receives the output of the comparator 420 via the inverter 424. The second switching device 426 receives the inverted output of the comparator 420 via a first input and receives the first PWM signal via a second input. In the example of FIG. 4, the switching device 426 is a logic OR gate. However, any active device may be used to implement the switching device 426 (e.g., a transistor, a circuit, etc.). Because the switching device 426 of the illustrated example is an OR gate, when the output of the comparator 420 is low, the output of the OR gate 422 will be high irrespective of the state of the first PWM signal. Thus, when the output of the comparator 420 is low, the OR gate blocks the first PWM signal.

On the other hand, when the output of the comparator 420 is high, the output of the OR gate 422 will completely depend on the first PWM signal. For example, when the output of the comparator 420 is high, the OR gate 426 receives a low signal via the inverter 424 and passes the first PWM signal.

Put another way, the switching device 426 has a first state in which it conveys a high voltage (i.e., when the voltage of the preprocessed audio signal does not exceed the DC bias voltage applied to the comparator 420). However, when the voltage of the preprocessed audio signal exceeds the voltage applied to the comparator 420, the switching device 426 has a second state in which it outputs the first PWM signal.

Thus, the mode selector 106 selects one of the switching devices 422 or 426 to convey a high voltage and one of the switching devices 422 or 426 to convey the first or second PWM signal at any given time depending on the amplitude of the preprocessed audio signal. For example, if the voltage of the audio signal exceeds the voltage of the DC bias 412, the mode selector 106 selects the switching device 422 to convey a high voltage (e.g., 3.3 volts) and selects the switching device 426 to convey the first PWM signal. Conversely, if the voltage of the preprocessed audio signal does not exceed the voltage of the DC bias 412, the mode selector 106 selects the switching device 422 to convey the second PWM signal and selects the switching device 426 to convey a high voltage.

The output of the switching device 422 is received by the high-side output driver 108. The high-side output driver 108 may be implemented by a first controller 430. The first controller 430 is in communication with the signal delivery circuitry 113. In the example of FIG. 4, the signal delivery circuitry 113 includes a first controller switch 432, a pass gate device 434, a diode 435, and a current feedback device 436. The first controller 430 receives the output of the OR gate 422. The first controller 430 is coupled to the control terminal of the first controlled switch 432 via a first output and is also coupled to the control terminal of the pass gate device 434 via a second output. The polarities of the first and second outputs of the first controller 430 are opposite to one another. In the example of FIG. 4, the controlled switch 432 may be implemented by a lateral double diffused metal-oxide semiconductor (LDMOS) transistor. However, any type of switch may be used.

The first controlled switch 432 receives the first output of the driver 430 via its gate. The drain of the first controlled switch 432 is coupled with a power supply 438 and a feedback device 436. The feedback device 436 is further coupled to an input of the first controller 430 to enable the first controller to limit the current of the driver 430. Limiting the current in this manner functions to limit the current through the energy storage device 111. This is important in implementations in which the energy storage device 111 is implemented by a surface mounted inductor which can only handle a limited amount of current. The source of the first controlled switch 432 is coupled with the pass gate device 434 and the energy storage device 111, 450. In the example of FIG. 4, the pass gate device 434 is formed by two N-channel metal-oxide semiconductor field effect transistors (MOSFET) having their sources coupled in series. The gates of the MOSFET devices receive the second output from the first controller 430 to couple or uncouple the energy storage device 111, 450 to/from the load 114 via the diode 435. The first controller 430 controls the first controlled switch 432 and the pass gate device 434 such that when the first controlled switch 432 is held on, the pass gates 434 are turned off, and when the first controlled switch 432 is being pulse width modulated (i.e., tracking the second PWM signal), the pass gate devices 434 are also being pulse width modulated (i.e., tracking the second PWM signal). As a result, when the first controller 430 receives the second PWM signal, the first controlled switch 432 couples the power supply 438 with the energy storage device 111, 450, and the pass gate device 434 couples the source of the first controlled switch 432 with the load 114. In this state, the pass gate device 434 is pulse width modulated to prevent current from flowing back from the load 114 into the first controlled switch 432. When the first controller 430 receives a constant high voltage, the pass gate device 434 is turned off and isolates the load 114 from the power supply 438. In this scenario, the energy storage device 450 is in series with the power supply 438 and the load 114 via a second pass gate device 444 as explained further below.

The output of the OR gate 426 is received by the low-side output driver 110. In the example of FIG. 4, the low-side output driver 110 is implemented by a second controller 440. Like the first controller 430, the second controller 440 is in communication with the signal delivery circuitry 113. In the example of FIG. 4, the signal delivery circuitry 113 includes a second controlled switch 442, a pass gate device 444, a diode 445, and a current feedback device 446. An output of the second controller 440 is coupled to the gate of the second controlled switch 442. In the example of FIG. 4, the second controlled switch 442 is implemented by an LDMOS device. In the example of FIG. 4, the drain of the second controlled switch 442 is coupled with the source of the first controlled switch 432 via the energy storage device 450. In the illustrated example, the energy storage device is implemented by an inductor 450.

The source of the second controlled switch 442 is coupled to ground 452 (e.g., a system ground, etc.). In the example of FIG. 4, the output terminal of the load 114 is also coupled to ground. The feedback device 446 is coupled with the source of the second controlled switch 442 to provide current feedback to the second controller 440. The feedback device 446 is included to limit the maximum current provided via the second controller 440. The drain of the second controlled switch 442 is coupled with the pass gate device 444. In the example of FIG. 4, the pass gate device 444 is formed by two P-channel MOSFET devices having their sources connected in series. The gates of the MOSFET devices implementing the pass gate device 444 receive an output from the second controller 440 to couple or uncouple the energy storage device 450 to/from the load 114.

The second controller 440 controls the second controlled switch 442 and the pass gates 444 such that the pass gates 444 are off when the second controlled switch is on, and the pass gates 444 are pulse width modulated (i.e., in accordance with the first PWM signal) when the second controlled switch 442 is pulse width modulated (i.e., also in accordance with the first PWM signal). As a result, when the pass gates 444 are held off, the second controlled switch 442 is turned on and couples the energy storage device 111, 450 with ground 452. When the second controlled switch 442 is pulse width modulated by the first PWM signal, the pass gates 444 are also pulse width modulated by the first PWM signal to prevent current from flowing from the load 114 into the drain of the second controlled switch 442.

The load 114 of the illustrated example is coupled with the input of the example circuit 400 via a feedback element 456. In the example of FIG. 4, the feedback element 456 is implemented with a resistor R_(F) 456. The feedback resistor R_(F) 456 and the input resistor R_(I) 401 form a feedback network that controls the overall gain of the example circuit 400.

As described above, when the voltage of the preprocessed audio signal exceeds a threshold (i.e., exceeds the reference voltage applied to the comparator 420), the OR gate 422 conveys a high voltage that is received by the first controller 430. At the same time, the OR gate 426 conveys the first PWM signal to the second controller 440. The first controlled switch 432 responds to the high voltage by turning on the first controlled switch 432. In other words, the first controlled switch 432 couples the power to supply 338 with the inductor 450. At the same time, the second output of the driver 430 turns off the pass gate device 434, thereby uncoupling the source of the boost device 432 from the load 114. In this configuration, the inductor 450 is in series with the power supply 438 and the load 114 via the pass gate 444. The pass gate device 444 receives the first PWM signal and selectively couples and uncouples the inductor with the diode 445 to prevent current feedback from the load 114 while driving the load with an amplified version of the input signal.

At the same time, the second controller 440 receives the first PWM signal via the OR gate 426. The pass gate devices 444 are configured to couple the drain of the second controlled switch 442 with the diode 445, which is further coupled to the load 114. The source of the second controlled switch 442 is also coupled with the ground 452. In this configuration, the signal delivery circuitry 113 is configured as a voltage booster.

FIG. 5A illustrates an example equivalent circuit schematic for the signal delivery circuitry 113 when configured as a voltage booster 500. The second controlled switch 442 is a switch that is opened and closed by the first PWM signal received via the OR gate 426. The first controlled switch 432 is held on (i.e., the switch 432 is closed and appears as a short) for the duration that the signal delivery circuitry 113 is configured as a voltage booster 500. A voltage booster 500 increases the output voltage beyond the input voltage supply based on the duty cycle of the switch 442. In other words, the output voltage swing from the boost converter 500 is boosted to have a larger voltage swing than the power supply 438 based on the first PWM signal.

In a voltage booster 500, the switch 442 is configured to open and short based on the first PWM signal. When the second controlled switch 442 is closed, current flows across the second controlled switch 442 and the inductor 450 stores the electric charge. In the example of FIG. 5A, the load 114 is implemented by a piezo-electric speaker, which is a capacitive element that stores and slowly releases energy. The diode 445 and pass gate devices 444 prevent the charge stored in the load 114 from flowing across the switch 442 when the switch 442 is closed. The energy stored by the load 114 therefore must slowly dissipate across the load 114, thereby reducing the energy stored in the load 114. The release of energy across the load 114 audibly presents the output audio to an end user. When the switch 442 opens, current from power supply 438 flows across the pass gate device 444 and the diode 445. At the same time, the inductor 450 releases the stored energy as a current, thereby causing the overall voltage swing to increase beyond the range of the voltage supply 438. In response to the increased current, the load 114 stores and dissipates energy to the ground 452. The load 114 thereby acts as a passive integrator and restores the output PWM signal as an analog signal which is audible to an end user.

Conversely, when the voltage of the audio signal does not exceed the voltage of the DC bias 412 applied to the comparator 420, the OR gate 426 conveys a high voltage that is received by the second controller 440. At the same time, the OR gate 422 conveys the second PWM signal to the first controller 430. The second controlled switch 442 receives the high voltage and couples the inductor 450 with ground, thereby configuring the inductor 450 in parallel with the power supply 438 and the load 114. At the same time, the second controller 440 turns off the pass gate device 444, thereby uncoupling the drain of the second controlled switch 442 from the load 114.

As mentioned above, the first controller 430 receives the second PWM signal via the OR gate 422. Using the second PWM signal, the first output of the first controller pulse width modulates the first controlled switch 432. The second output of the first controller 430 also pulse width modulates the pass gate device 434 to prevent current from flowing from the load 114 back into the inductor 450. In this configuration, the signal delivery circuitry 113 is configured as a voltage buck-booster.

FIG. 5B illustrates an example schematic of an equivalent circuit for the signal delivery circuitry 113 when configured as a voltage buck-booster 550. The second controlled switch 432 is represented by a switch that opens and closes based on the second PWM signal. The second controlled switch 442 is held on (i.e., the switch 432 is closed and appears as a short) for the duration that the signal delivery circuitry 113 is configured as a voltage booster 500. A voltage buck-booster 550 decreases the output voltage below the low output signal (i.e., the ground) based on the duty cycle of the second controlled switch 432. Additionally, the voltage buck-booster 550 produces current through the load having an inverses polarity from the current produced when the circuitry 113 is configured as a voltage booster (i.e., the voltage swing will be negative). Thus, the output voltage swing from the voltage buck-booster 550 is boosted to have a larger magnitude than the power supply 438 based on the second PWM signal, however the voltage swing will be negative.

In a voltage booster 550, the switch 432 is configured to open and short based on the second PWM signal When the first controlled switch 442 is closed, current flows across the second controlled switch 442 and the inductor 450 stores the electric charge. In the example of FIG. 5B the load 114 is implemented by a piezo-electric speaker, which is a capacitive element that stores and slowly releases energy. In the voltage buck-booster 550, current from the power supply 438 flows into the inductor 450 and stores a charge in the inductor 450. At the same time, the load 114 has a charge stored and the diode 435 prevents the load 114 from dissipating the energy across the switch 432, thereby allowing the load to slowly dissipate energy across the capacitive load. When the switch 432 opens, the power supply 438 is uncoupled and the inductor releases the charge into the load 114. The load 114 accumulates and dissipates the energy released by the inductor 450. As described above, the load 114 thereby acts as a passive integrator and restores the output PWM signal as an analog signal that is audible to an end user.

A feedback element 454 further couples the audio interface 114 with the first integrator 404. As described above, the feedback element 454 provides a feedback path to control the gain of the example circuit 400 based on the feedback element 454 and the input resistance 401.

FIG. 6 illustrates the example ground-referenced audio amplifier 100 of FIG. 1 in an example environment of use, namely, in an example wireless communication device 600. The example wireless communication device 600 may be a mobile telephone (e.g., a cell phone, a wireless messaging device, etc.), a pager, a laptop computer, a wireless game device, an MP3 player, etc. The example wireless communication device 600 includes a processor 602, a ground-reference audio amplifier 100, a display 608, a plurality of keys (e.g., buttons) 610, and a microphone 612, all of which may be communicatively coupled to the example processor 602. In the illustrated example, the wireless communication device 600 includes a speaker 606 that is communicatively coupled to the example processor 602 via the example ground-reference audio amplifier 100.

The example wireless communication device 600 also includes a wireless communication transceiver 614 that is communicatively coupled to an antenna 616. The wireless communication transceiver 614 may be implemented using, for example, WiMAX technology, wireless Ethernet technology (e.g., 802.11(b), etc.), CDMA technology, TDMA technology, GSM technology, analog/AMPS technology, Wireless USB technology, and/or any other suitable past, present or future mobile communication technology. Then example processor is communicatively coupled to the wireless communication transceiver 614 to selectively use the wireless communication transceiver 614 to, for example, communicate with a wireless base station (not shown). The wireless communication device 600 of the illustrated example also includes other electronics hardware such as, for example, a Bluetooth® transceiver and/or an 802.11 (i.e., Wi-Fi®) transceiver, either of which may be communicatively coupled to the example processor 602.

FIGS. 7A-D illustrates a more detailed example implementation of the ground-referenced audio amplifier of FIGS. 1 and/or 4. In the example of FIGS. 7A-D, the input interface 102 is implemented by a resistor 701, a level shifter 702, a first integrator 704, a second integrator 706, a summing device 708, and a DC bias 712. As described above, the input interface suppresses the noise so that substantially all of the noise is inaudible to the human ear. As illustrated in FIGS. 7A and 7B, the example input interface 102 conveys the preprocessed audio signal to the PWM 104, which includes a first comparator 714 and a second comparator 716. As described above, the first comparator produces a first PWM signal and the second comparator produces a second PWM signal. The first and second PWM signals are received by the mode selector 106. In the example of FIG. 7B, the mode selector 106 is implemented by a comparator 720, a first OR gate 722, an inverter 724, and a second OR gate 726. The mode selector 106 either conveys a high voltage or one of the first and second PWM signal as explained above.

The first high-side output driver 108 receives the second PWM signal or a high voltage from the OR gate 722. In the example of FIGS. 7B and 7C, the high-side output driver 730 is implemented by an AND gate 730 and an inverter 731. The AND gate 730 forms a first output of the driver 108 and the inverter 731 forms a second output of the driver 108. The AND gate 730 also receives a signal from a current feedback device 736, which is illustrated in the example of FIG. 7B. The second high-side output driver 740 receives the first PWM signal or a high voltage from the OR gate 726. Additionally, the second high-side output driver receives a signal from the current feedback device 736.

The AND gate 730 conveys either the second PWM signal or a high voltage to a first LDMOS device 432. The AND gate 740 conveys either the first PWM signal or the high voltage to a second LDMOS device 442. The first and second LDMOS transistors, along with a first pass gate device 734, a second pass gate device 744, a first diode 735, and a second diode 735 implement the signal delivery circuitry 113 of FIG. 1A. In the example of FIG. 7C, the energy storage device 111 is implemented by an inductor 750. The signal delivery circuitry 113 of FIG. 7C, which is powered by the power supply 738, and the inductor 111 of FIG. 7C outputs a signal representative of the input audio signal, but with a larger voltage swing than the voltage of the power supply 738. The output signal is received by the load 114, which is referenced to ground (e.g., a system ground, etc.). In addition, the example of FIG. 7 may also include a capacitor 760 to implement the signal delivery circuitry 113, but inclusion of the capacitor is dependent on the type of load 114. For example, implementing the load 114 as a piezo-electric speaker may enable elimination of the capacitor because a piezo-electric speaker is a capacitive load. The example of FIG. 7D illustrates additional devices that may be implemented to reduce voltage and current spikes in the illustrated examples. In particular, FIG. 7D illustrates a timing circuit that functions to achieve leading edge blanking to prevent switching at the highs and lows of the triangle reference signal so that the duty cycle of the first and/or second PWM signals does not go to 100%.

Although certain methods, systems, and articles of manufacture have been described herein, the scope of coverage of this patent is not limited thereto. To the contrary, this patent covers all methods, systems, and articles of manufacture fairly falling within the scope of the appended claims either literally or under the doctrine of equivalents. 

1. An apparatus to amplify an audio input signal, comprising: a first driver to receive a first signal; a second driver to receive a second signal; a configurable signal delivery circuit; and a mode selector in communication with the first and second drivers to selectively configure the signal delivery circuit in a voltage boost mode or a voltage buck-boost mode based on a characteristic of the input signal.
 2. An apparatus as defined in claim 1, wherein the first signal is a first pulse-width modulated signal, and the second signal is a second pulse-width modulated signal.
 3. An apparatus as defined in claim 2, further comprising a pulse-width modulator configured to generate the first pulse-width modulated signal the second pulse-width modulated signal based on the input signal.
 4. An apparatus as defined in claim 3, wherein the pulse-width modulator is to generate the first pulse-width modulated signal by comparing the input signal to a reference signal.
 5. An apparatus as defined in claim 1, wherein the characteristic of the input signal is a voltage amplitude of the input signal.
 6. An apparatus as defined in claim 1, further comprising an energy storage device in communication with the signal delivery circuit.
 7. An apparatus as defined in claim 6, wherein the signal delivery circuit delivers an output signal having a voltage greater than a voltage of a power supply powering the apparatus.
 8. An apparatus as defined in claim 6, wherein the signal delivery circuit delivers a first voltage having a first polarity when in the voltage boost mode and a second voltage having a second polarity when in the voltage buck-boost mode, the first polarity being opposite the second polarity.
 9. An apparatus as defined in claim 6, wherein the energy storage device comprises an inductor.
 10. An apparatus as defined in claim 1, wherein the signal delivery circuit comprises: a first transistor having a first condition in which the first transistor couples an energy storage device to a power supply and a second condition in which the first transistor is driven by the first signal; a first pass gate having a first state in which the first pass gate disconnects a first path between the first transistor and a load, and a second state in which the first pass gate is driven by the first signal; a second transistor having a first condition in which the second transistor couples the energy storage device to ground and a second condition in which the second transistor is driven by the second signal; and a second pass gate having a first state in which the second pass gate disconnects a second path between the second transistor and the load, and a second state in which the second pass gate is driven by the second signal.
 11. An apparatus as defined in claim 10, wherein, when the signal delivery circuit is in the voltage boost mode, the first transistor is in the first condition, the first pass gate is in the first state, the second transistor is in the second condition and the second pass gate is in the second state.
 12. An apparatus as defined in claim 10, wherein, when the signal delivery circuit is in the voltage buck-boost mode, the first transistor is in the second condition, the first pass gate is in the second state, the second transistor is in the first condition and the second pass gate is in the first state.
 13. An apparatus as defined in claim 1, further comprising a transducer in communication with the signal delivery circuit.
 14. An apparatus as defined in claim 13, wherein the transducer is a single sided device.
 15. (canceled)
 16. An apparatus as defined in claim 13 wherein the transducer is coupled to the signal delivery circuit without a coupling capacitor.
 17. A method to amplify an audio input signal, comprising: modulating the audio input signal to produce a first signal and a second signal; comparing a characteristic of the audio input signal to a reference; configuring a signal delivery circuit in a voltage boost mode or a voltage buck-boost mode based on the comparison; and producing an output signal using one of the first or the second signals.
 18. A method as defined in claim 17, wherein the first signal is a first pulse-width modulated signal, and the second signal is a second pulse-width modulated signal, and the first and second signals have opposite polarities.
 19. A method as defined in claim 17, wherein modulating the audio input signal comprises comparing the audio input signal to a reference signal.
 20. A method as defined in claim 17, wherein the characteristic of the input signal is a voltage of the input signal.
 21. A method as defined in claim 17, wherein the output signal has a voltage greater than a voltage of a power supply.
 22. A method as defined in claim 17, wherein the output signal has a first voltage and a first polarity in the voltage boost mode, and the output signal has a second voltage and a second polarity when in the voltage buck-boost mode, the first polarity being opposite the second polarity.
 23. A method as defined in claim 17, wherein configuring the signal delivery circuit in the voltage boost mode comprises: placing a first transistor in a state in which the first transistor couples an energy storage device to a power supply; placing a first pass gate in a state in which the first pass gate disconnects a first path between the first transistor and a load; placing a second transistor in a state in which the second transistor is driven by the second signal; and placing a second pass gate in a state in which the second pass gate is driven by the second signal.
 24. A method as defined in claim 23, wherein configuring the signal delivery circuit in the voltage buck-boost mode comprises: placing the first transistor in a state in which the first transistor is driven by the first signal; placing the first pass gate in a state in which the first pass gate is driven by the first signal; placing the second transistor in a state in which the second transistor couples the energy storage device to ground; and placing the second pass gate in a state in which the second pass gate disconnects a second path between the second transistor and the load.
 25. A method as defined in claim 17, further comprising transducing the output signal of the signal delivery circuit into a humanly audible sound.
 26. A mobile device comprising; a housing; an input device; a communication device to send and receive information; a power supply having a first voltage; a transducer; an amplifier to amplify an audio input signal received via the communication device, the amplifier comprising: a first driver to receive a first signal; a second driver to receive a second signal; a configurable signal delivery circuit; and a mode selector in communication with the first and second drivers to selectively configure the signal delivery circuit in a voltage boost mode or a voltage buck-boost mode based on a characteristic of the input signal, the signal delivery signal to deliver an output signal comprising an amplified version of the input signal to the transducer, the signal delivery signal being adapted to selectively deliver a second voltage higher than the first voltage. 